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(Online) ISSN 2744-1741 
Defense and Security Studies  Original Research 
Vol. 5, No. 1, 2024, pp. 20-28 
https://doi.org/10.37868/dss.v5.id204 

 

This work is licensed under a Creative Commons Attribution License (https://creativecommons.org/licenses/by/4.0/) that allows others 
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authorship and initial publication in this journal. 

 20 

 
 
Sub-6GHz hand pump shaped microstrip antenna for 5G 
communication 
 
Adnan Ahmetović1*, Şehabeddin Taha Imeci2, Bilal Tütüncü3 
1 Electrical and Electronics Engineering, Faculty of Engineering and Natural Sciences, International University of Sarajevo, Bosnia 
and Herzegovina 
2 College of Engineering and Technology, American University of the Middle East, Kuwait 
3 Electrical and Electronics Engineering, Faculty of Engineering, Van Yüzüncü Yıl University, Van, Turkey 
 

 
*Corresponding author E-mail:  adnan.ahmetovic0@gmail.com  

Received: Dec.10, 2023 
Revised: Feb. 1, 2024.  
Accepted: Mar. 3, 2024 
Online: Mar. 8, 2024. 

Abstract 
The purpose of this paper is to explore the presented design of a hand-pump 
shaped microstrip antenna pfor sub-6GHz 5G communication. This paper will 
first provide a brief overview of the antenna design and its capabilities. Meaning, 
overall impressive dimensions of 25.25 mm x 20.75 mm x 1.55 mm, with S11 
being -16.82 dB at operating frequency of 5.16 GHz. Next, the paper will discuss 
the design of the antenna and how it can be optimized with sub 6 GHz operating 
frequency, along with requirements. To reach required specifications, inc. E-𝜃 ≥ 5 
GHz ≥ E-φ; S11 ≤-10, various geometrical parameters, among others, have been 
tested, resulting in two slots being added (slot a and slot b), in combination with 
various slits. Finally, antenna is produced, and laboratory measurements are 
carried out for the validation of results. Further discussing potential benefits and 
drawbacks of using this antenna design for 5G applications. 

© The Author 2024. 
Published by ARDA. Keywords: hand-pump antenna, 5G, antenna analysis, sonnet software 

1. Introduction 

5G networks operate in a higher frequency range than previous generations, allowing for faster speeds and 
more capacity. 5G signals are able to travel further and penetrate buildings better than previous generations, 
making it ideal for coverage in dense urban areas. 5G technology is also more energy efficient than earlier 
generations, meaning that service providers can deploy more 5G base stations without increasing power 
consumption. In terms of frequencies used, the 3.4 GHz-3.8 GHz band is at the forefront of the sub-6 GHz 
spectrum. Many countries see this band as a pioneer in realizing 5G technologies such as massive MIMO 
arrays and antennas [1-3]. In recent literature, there has been significant interest increase towards microstrip 
antennas, inc. single element antennas, MIMO antennas and arrays, for 5G application [4]. This paper is 
focused towards single element hand-pump shape microstrip patch antenna, using fr4 dielectric, which is 
known to have return loss is much lower compared to the other dielectric materials typically being used [5]. 
Based on the researches, we can see that both square and rectangular shaped microstrip patch antenna offers 
satisfactory value of return loss (S11), that can be reduced by proper selection of material and shape of the 
antenna [6, 7]. Antenna’s shape fine design usually includes various slits and slots, which alter antenna 
parameters, by change of current distribution, along with use of different thicknesses [8, 9].  

Based on the findings, we can conclude that using a substrate material with a greater dielectric constant 
degrades antenna performance while reducing antenna size. With increase of substrate thickness, the 



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resonance frequency results in decrease, in contrast to the bandwidth, which increases [10-11]. Paper [12] 
even suggests use of U Slotted Patch, along Air substrate, for better performance in terms of Gain. However, 
focus of this paper will achievement of desired parameters, which includes specifical vertical and horizontal 
polarization required values (- E-𝜃 ≥ 5 GHz ≥ E-φ), along with return loss (S11 ≤-10). Most of the wireless 
networks such as 5G require multiband MIMO-supported Base Station Antennas and achieve this with use of 
multiple ports, supporting wider range of frequencies, leading to multiple arrays within one compact antenna 
enclosure [13-15]. Paper [16] suggests employment of a single layer cross bow-tie dual-band tunable HIS 
(high-impedance surface) antenna designed for UHF band.  

There is also the potential use of a waveguide simulator to characterize approximately the performance of the 
proposed metamaterial structure [17]. Patch array smart antennas can be used to arrange radiation patterns that 
cannot be achieved with a single patch element [18]. However, these structures of antennas require larger 
space, some have poor radiation efficiency and narrower bandwidth. Therefore, the focus of this paper, along 
others (S11, E-𝜃,  E-φ) will be achievement of wider bandwidth, smaller size, and high gain performance at 
LTE 42/43 (3.4 GHz–3.8 GHz) band for 5G communication. This single band antenna is designed and 
analyzed in sonnet software [19], but also experimentally made. In addition, there is a lack of literature 
describing geometrical optimization of similar antennas. References [20] and [21] investigate the effect of the 
gap between radiating patches, but they do not take this into account to optimize the dimension parameters of 
a single-band antenna.  

2. Method 

Figure 1. represents Schematic Diagram of the Microstrip Patch Antenna, along with antenna dimensions. The 
design was created by joining together two rectangular shaped pieces. Antenna has dimensions of 25.25 mm x 
20.75 mm x 1.55 mm and it is fed up via port in the bottom right. This configuration provided the best current 
distribution results. Design was created and simulated in Sonnet software, later on produced and 
experimentally tested. Initial design didn’t satisfy required specifications, in terms of reflection loss (S11), so 
slits on the bottom right part were added, they improved S11 drastically, but still the E-θ was not sufficient, 
showing value much greater than -5 dB. To improve current distribution, along E-θ, a large slot in the middle 
was added, which resulted in value closer to the required -5 dB, but not yet sufficient. Furthermore, design 
was greatly improved, by detailed parametric analysis, resulting in two slots on the right, with one large slit in 
the middle, which, along dimension tweaking, provided sufficient results. More discussion along antenna 
dimensions can be seen in the Parametric Analysis part.   

 
Figure 1. Schematic diagram of the microstrip patch antenna  



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Figure 2. represents 3D view of the antenna. It is noted that dielectric substrate material being used is FR4, 
with thickness of 1.55 mm. Already mentioned antenna feeding line, width of 1mm is drilled, so that port 
could be attached. For simulation purposes, box size was selected to be 10x larger than antennas dimensions, 
resulting in size of 225 mm x 255 mm. In this means cell size was 0.25 mm x 0.25 mm, which was minimum, 
limited by universities R&D equipment, preventing any circular elements in antenna’s design, since they 
required smaller cell size to be properly design and simulated.  

 

Figure 2. 3D view of the microstrip patch antenna 

3. Results 

Data shown below represents Parametric Analysis of proposed design. A parametric analysis was carried out 
by varying the dimensions of length and width of various antenna parts, as well as dielectric thickness and erel 
value. Analysis consists of 7 tables, where the first 3 tables represent size variations, Table 4 being Erel Value 
(𝜀  in tables), Table 5 dielectric thickness and Table 6 and Table 7 are combination of previously done 
variations, with goal of choosing best value for every parameter.  

Table 1. represents size variation of a Slot (a) (smaller slot on the right antenna side). It is noted that narrower 
slot design will result in S11 value fluctuation, with tendency to lower down, no matter the length. Value of 3 
mm x 0.75 mm provided E-φ increase, but significantly decreases S11 value, therefore dimension of 2 mm x 1 
mm is chosen. 

Table 1. Size of the slot (a) 

Dimension / mm S11/ dB   Frequency / GHz E-φ / dB E-θ / dB 

2 x 0.5  -13.71   5.26  5.362  -5.033  

2 x 0.75  -13.85   5.26  5.372  -5.035  

2.25 x 0.7 -13.63   5.26  5.382  -5.037  

3 x 0.75  -12.81   5.24  5.414  -5.034  

2 x 1 -13.90  5.26  5.384  -5.040  

In Table 2., various dimensions have been proposed for Slot (b) (larger slot on the center part of the antenna), 
and it is noted that the length of the slot and S11 parameter are directly proportional, resulting in significant 
S11 value increase with length increase. Although S11 value has greatly increased, this option was not 
suitable, because E-θ value fell down below required (-5 dB), therefore, bolded dimensions were 
implemented.  



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Table 2. Size of the slot (b) 

Slot-(b) Size/mm S11/dB Frequency/GHz E-φ/dB E-θ/dB 

1.25 x 8 -13.70  5.26  5.343  -5.040  

1.5 x 8 -15.24   5.22  5.379  -4.956 

1.5 x 8.5 -20.36   5.12  5.262  -4.859 

2.5 x 8.5 -18.14  4.98  5.145  -4.705 

2 x 8.5 -18.45   5.06  5.389  -4.651 

Table 3 represents results of various Slit dimensions (side rectangle on the bottom right of the antenna). 
Although some dimensions provided better E-φ and E-θ values, dimensions of 0.75 mm x 0.5 mm resulted in 
great S11 increase, hence it was more suitable. Less than 0.5 mm almost always resulted in E-φ decreas, in 
this case S11, also decreased.  

Table 3. Size of the slits 

Slits Size/mm S11/dB Frequency /GHz E-φ/dB E-θ /dB 
1 x 0.5 -13.90   5.26  5.384 -5.040 

1.25 x 0.5 -11.89  5.26  5.410 -5.026 
1.5 x 0.5 -10.12  5.26  5.422 -5.093 
0.75 x 0.5 -15.56   5.26  5.344 -5.026 
0.75 x 0.25 -14.92  5.26  5.290 -5.026  

Table 4. represents experimentation with Erel Value, it is noted that Erel Value of 4.6, although lowering the 
operating frequency of the antenna, increases both E-φ and E-θ, as well as S11, to -16.92 dB. Erel being lower 
than 4.4 results in E-θ decreasing below the required value of -5 dB.  

Table 4. Erel value 

𝜀  S11/dB Frequency/GHz E-φ/dB E-θ/dB 

4.4 -15.56 5.26 5.344 -5.026 
4.5 -15.04 5.2 5.263 -5.121 
4.6 -16.82 5.16 5.350 -5.147 
4.3 -15.17  5.32 5.401 -4.931 
4.2 -14.57 5.38 5.440 -4.844 

Table 5. represents Dielectric Thickness fluctuation, while sticking to design default Erel Value of 4.2, note 
that any value less than 1.70 of diel. Thickness results in S11 above -15 dB, but any value lower than 1.55, 
reduces E-θ to less than -5 dB. With this, we can neglect the benefits of increased E-φ and S11 and stick to the 
value of 1.55. 

Table 5. Dielectric thickness with erel value- (4.2) 
Dielectric Thickness 

(𝜀 - 4.2) 
S11/dB Frequency/GHz E-φ/dB E-θ/dB 

1.55 -15.56  5.26 5.344 -5.026 
1.6 -13.87  5.38 5.415 -4.765 
1.65 -13.31  5.38 5.393 -4.683 
1.52 -15.02  5.38 5.456 -4.890 
1.45 -15.99  5.38 5.499 -4.988 



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In Table 6., we can see that now with Erel being value of 4.6, E-θ satisfies the requirements in every case, this 
provided ability to start experimenting with Dielectric Thickness more freely than before, hence value of 
dielectric thickness greater than 1.55 is not necessary, since it has negative result on S11, E-φ and E-θ. There 
is no need to lower down Diel. Thickness value, less than 1.55, since it satisfied the requirements, thicker 
dielectric layer can result in a more stable antenna design, while additionally increasing the power handling 
capability of the antenna.  

Table 6. Dielectric thickness with erel value- (4.6) 
Dielectric Thickness  

(𝜀 - 4.6) 
S11/dB Frequency/GHz E-φ/dB E-θ/dB 

1.55 -16.82 5.16 5.350 dB -5.147 dB 
1.6 -15.96 5.16 5.327 dB -5.076 dB 
1.65 -12.43  5.14 5.117 dB -5.106 dB 
1.52 -17.26  5.16 5.365 dB -5.188 dB 
1.45 -17.95  5.16  5.407 dB -5.276 dB 

Hence the above, Table 7 is representation of all the combined values, examining the S11 and radiation 
efficiency of the proposed antenna due to the optimized size parameters based on simulated results to achieve 
optimum values. 

Table 7. Final parameters with chosen values. 
Parameter Value S11 Frequency  E-φ  E-θ 

Dielectric Thickness  1.55 mm -16.71 dB  (5.16 GHz) 5.333 dB -5.180 dB 
𝜀  4.6 

Slot (a) 2 mm x 1 mm 
Slot (b) 1.25mm x 8mm  

Slit 0.75mm x 0.5mm 

4. Discussion  

S-parameters are shown below (Figure 3.), specifically S11, representing reflection loss of the antenna. 
Already mentioned goal was to achieve S11 value of  ≤ -10 dB, by this means S11 provided -16.71 dB, as 
seen below. This implies an operational frequency of 5.16 GHz, with an operational bandwidth of exactly 60 
MHz. Furthermore, performance was studied with the help of antenna gain, current distribution, radiation 
pattern and radiation efficiency, specifical component shown in Figure 4 and Figure 5.    

 
Figure 3. S-parameters of the microstrip patch antenna 



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Vertical polarization component (E-θ ) is presented in Figure 4. Below, showing that E-θ is equal to -5.18 dB, 
at its peak point (50°), in operational frequency (5.16 GHz). This graph was the main point of concern, at 
particular the moment, since reaching desired values required numerus geometrical changes in antennas 
design.  

 
Figure 4. E-θ of the microstrip patch antenna 

Horizontal polarization component (E-𝜑) is presented in Figure 5. It implies that E-φ reaches 5.333 dB, peak 
5°. The presented simulation was done at frequency of 5.16 GHz. Moreover, in Figure 6. presenting Far Field 
with polar view including all curves together, it is noted that radiation pattern satisfied all the requirements.  

 
Figure 5. E-φ of the microstrip patch antenna 

Presented Figure 6. considers all radiation pattern curves together in polar view, together with E-Total 
represented in yellow color. Red colored curve represents horizontal axis (E-𝜑), while vertical axis (E-θ) is 
represented in blue color. From the figure, the radiation pattern curves are close to symmetrical. Additionally, 
the maximum radiation intensity is located at the Theta=5°, showing 5.56 dB E-Total. 



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Figure 6. Radiation pattern of microstrip antenna 

Figure 7. is showing circular E-Total polarization in 3D view, considering power gain with included 
reflection. Magnitude Scale is shown on the left. It can be seen that the polarization is quite good, with 
reflection well within the acceptable range, since values remand remarkably close to original. 

 
Figure 7. E-Total 3D view of microstrip patch antenna 

Figure 8. represents current distribution diagram of presented antenna design, at 5.16 GHz. It is noted that 
current has tendency to flow from edges of the antenna to middle parts. This was the exact reason for adding 
large slot in the middle part. Graph proves that mentioned slot, increased current desnsity in area to values 
greater than 10 A/m. It can be seen that feeding line also, along with bottom right part plays particular role in 
current distribution, since changes in mentioned area, had lowered the magnitude in right part for 
consequence. By understanding the current distribution, the antenna design can be further improved to achieve 
better performance. 



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Figure 8. Current distribution of the microstrip patch antenna 

In conclusion the proposed microstrip patch antenna shown in the paper, provides reflection loss of S11=-
16.71 dB, E-φ of 5.333 dB and E-θ of -5.18 dB. This provides more than sufficient values for the sub 6GHz 
range. The design and geometrical optimization resulted in operational frequency of 5.16 GHz, with incredible 
dimensions, especially considering other single element-single port designs. Simulation was obtained using 
ABS sweeps, 0 GHz to 6 GHz, respectively. Furthermore, the proposed antenna design could be considered as 
a choice for 5G applications due to its high current density capability and small size. The slot in the middle 
part of the antenna plays the key role in increasing the current density, while the feeding line and the bottom 
right part also contribute to the current distribution. On the other hand, future geometrical improvements could 
be made with usage of optimization algorithms. 

Funding information 

This research received no specific grant from any funding agency in the public, commercial, or not-for-profit 
sectors. 

Declaration of competing interest 

The authors declare that they have no known competing financial interests or personal relationships that could 
have appeared to influence the work reported in this paper. 

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